2002 Microchip Technology Inc.

DS21347B-page 1

Features

· Combines Two Op Amps, Two Comparators and

a Voltage Reference in a Single Package

· Optimized for Single-Supply Operation

· Small Package: 16-Pin QSOP

· Ultra Low Input Bias Current: Less than 100pA

· Low Quiescent Current: Operating 16

A (Typ.)

Shutdown 6

A (Typ.)

· Rail-to-Rail Inputs and Outputs

· Operates Down to V

= 1.8V

· Reference and One Comparator Remain Active in

Shutdown to Provide Supervisory Functions

Applications

· Power Management Circuits

· Battery Operated Equipment

· Consumer Products

· Replacements for Discrete Components

Device Selection Table

Package Type

General Description

The TC1043 is a mixed-function device combining two
general purpose op amps, two general purpose com-
parators, and a voltage reference in a single 16-Pin
package.

This increased integration allows the user to replace
two or three packages, saving space, lowering supply
current, and increasing system performance. A shut-
down input, SHDN, disables the op amps and one of
the comparators, placing their outputs in a high-imped-
ance state. The reference and one comparator stay
active in shutdown mode. Standby power consumption
is typically 6

A. Both the op amps and comparators

have rail-to-rail inputs and outputs which allows opera-
tion from low supply voltages with large input and out-
put signal swings.

Packaged in a 16-Pin QSOP, the TC1043 is ideal for
applications requiring high integration, small size and
low power.

Part Number

Package

Temperature

Range

TC1043CEQR

16-Pin QSOP

-40°C to +85°C

TC1043

_EQR

IN+

OUT

IN+

OUT

SHDN

REF

16-Pin QSOP

TC1043

Linear Building Block Low Power Voltage Reference with

Dual Op Amp, Dual Comparator, and Shutdown Mode

TC1043

DS21347B-page 2

2002 Microchip Technology Inc.

1.0

ELECTRICAL
CHARACTERISTICS

ABSOLUTE MAXIMUM RATINGS*

Supply Voltage ......................................................6.0V

Voltage on Any Pin ........... (V

0.3V) to (V

+0.3V)

Junction Temperature....................................... +150°C

Operating Temperature Range............. -40°C to +85°C

Storage Temperature Range .............. -55°C to +150°C

*Stresses above those listed under "Absolute Maximum
Ratings" may cause permanent damage to the device.
These are stress ratings only and functional operation of the
device at these or any other conditions above those indi-
cated in the operation sections of the specifications is not
implied. Exposure to Absolute Maximum Rating conditions
for extended periods my affect device reliability.

TC1043 ELECTRICAL SPECIFICATIONS

Electrical Characteristics: Typical values apply at 25°C and V

= 3V. Minimum and maximum values apply for T

= -40° to

+ 85°C, and V

= 1.8V to 5.5V, unless otherwise specified.

Symbol

Parameter

Min.

Typ

Max

Units

Test Conditions

Supply Voltage

1.8

5.5

Supply Current Operating

All outputs unloaded,
SHDN = V

SHDN

Supply Current, Shutdown

CMPTR2 and V

REF

Outputs

unloaded, SHDN = V

Shutdown Input

Input High Threshold

80% V

Input Low Threshold

20% V

Shutdown Input Current

±100

Op Amps

SEL

Select Time

sec

OUT

from SHDN = V

)

= 10k

to V

DESEL

Deselect Time

100

nsec

OUT

from SHDN = V

)

= 10k

to V

OUT

(SD)

Output Resistance in Shutdown

SHDN = V

OUT

(SD)

Output Capacitance in Shutdown

SHDN = V

VOL

Large Signal Voltage Gain

100

V/mV

= 10k

, V

= 5V

ICMR

Common Mode Input Voltage Range

- 0.2

+ 0.2

Input Offset Voltage

±100

±0.3

±500

±1.5

= 3V, V

= 1.5V, T

25°C, T

= -40°C to 85°C

Input Bias Current

-100

100

= 25°C, V

= V

to V

OS(DRIFT)

Input Offset Voltage Drift

±4

V/°C

= 3V, V

= 1.5V

GBWP

Gain-Bandwidth Product

kHz

= 1.8V to 5.5V

= V

to V

Slew Rate

mV/

sec

= 100pF

= 1M

to GND

Gain = 1
V

= V

to V

OUT

Output Signal Swing

+ 0.05

- 0.05

= 10k

CMRR

Common Mode Rejection Ratio

= 25°C, V

= 5V

= V

to V

PSRR

Power Supply Rejection Ratio

= 25°C, V

= V

to V

SRC

Output Source Current

IN+ = V

, IN- = V

Output Shorted to V

= 1.8V, Gain = 1

SINK

Output Sink Current

IN+ = V

, IN- = V

Output Shorted to V

= 1.8V, Gain = 1

Input Noise Voltage

0.1Hz to 10Hz

Input Noise Voltage Density

125

nV/

Hz 1kHz

2002 Microchip Technology Inc.

DS21347B-page 3

TC1043

TC1043 ELECTRICAL SPECIFICATIONS (CONTINUED)

Electrical Characteristics: Typical values apply at 25°C and V

= 3V. Minimum and maximum values apply for T

= - 40° to + 85°C, and

= 1.8V to 5.5V, unless otherwise specified.

Symbol

Parameter

Min.

Typ

Max

Units

Test Conditions

Comparators

OUT

(SD)

Output Resistance in Shutdown

SHDN = V

OUT

(SD)

Output Capacitance in Shutdown

SHDN = V

SEL

Select Time (For Valid Output)

sec

OUT

from SHDN = V

=10k

to V

DESEL

Deselect Time

500

nsec

OUT

from SHDN = V

=10k

to V

ICMR

Common Mode Input Voltage Range

0.2

+ 0.2

Input Offset Voltage

5
5

+5
+5

= 3V, V

= 1.5V

= 25°C

= -40°C to 85°C

Input Bias Current

±100

= 25°C,

IN+, IN- = V

to V

Output High Voltage

0.3

= 10k

to V

Output Low Voltage

0.3

= 10k

to V

CMRR

Common Mode Rejection Ratio

= 25°C, V

= 5V

= V

to V

PSRR

Power Supply Rejection Ratio

= 25°C, V

= 1.2V

= 1.8V to 5V

SRC

Output Source Current

IN+ = V

, IN- = V

Output Shorted to V

= 1.8V

SINK

Output Sink Current

IN+ = V

, IN- = V

DD,

Output Shorted to V

= 1.8V

PD1

Response Time

sec

100mV Overdrive, C

= 100pF

PD2

Response Time

sec

10mV Overdrive, C

= 100pF

Voltage Reference

REF

Reference Voltage

1.176

1.200

1.224

REF(SOURCE)

Source Current

REF(SINK)

Sink Current

L(REF)

Load Capacitance

100

VREF

Voltage Noise

RMS

100Hz to 100kHz

Noise Density

1.0

Hz 1kHz

2002 Microchip Technology Inc.

DS21347B-page 5

TC1043

3.0

DETAILED DESCRIPTION

The TC1043 is one of a series of very low power, linear
building block products targeted at low voltage, single
supply applications. The TC1043 minimum operating
voltage is 1.8V and typical supply current is only 20

(fully enabled). It combines two comparators, two op
amps and a voltage reference in a single package. A
shutdown mode is incorporated for easy adaptation to
system power management schemes. During shut-
down, all but one comparator and the voltage reference
are disabled (i.e. powered down with their respective
outputs at high impedance). The "still awake" compar-
ator and voltage reference can be used as a wake-up
timer, power supply monitor, LDO controller or other
continuous duty circuit function.

3.1

Comparators

The TC1043 contains two comparators. The compara-
tors input range extends beyond both supply voltages
by 200mV and the outputs will swing to within several
millivolts of the supplies, depending on the load current
being driven.

The comparators exhibit a propagation delay and sup-
ply current which are largely independent of supply
voltage. The low input bias current and offset voltage
make them suitable for high impedance precision appli-
cations.

Comparator CMPTR1 is disabled during shutdown and
has a high impedance output. Comparator CMPTR2
remains active.

3.2

Operational Amplifiers

The TC1043 contains two rail-to-rail op amps. The
amplifiers' input range extends beyond both supplies
by 200mV and the outputs will swing to within several
millivolts of the supplies depending on the load current
being driven.

The amplifier design is such that large signal gain, slew
rate and bandwidth are largely independent of supply
voltage. The low input bias current and offset voltage of
the TC1043 make it suitable for precision applications.
Both op amps are disabled during shutdown and have
high output impedance.

3.3

Voltage Reference

A 2.0% tolerance, internally biased, 1.20V bandgap
voltage reference is included in the TC1043. It has a
push-pull output capable of sourcing and sinking at
least 50

A. The voltage reference remains fully

enabled during shutdown.

3.4

Shutdown Input

SHDN at V

disables both op amps and one compara-

tor. The SHDN input cannot be allowed to float. When
not used, connect it to V

. The disabled comparator's

output and the two disabled op amp outputs are in a
high impedance state when shutdown is active. The
disabled comparator's inputs and the two disabled op
amp inputs can be driven from rail-to-rail by an external
voltage when the TC1043 is in shutdown. No latch-up
will occur when the device is driven to its enabled state
when SHDN is set to V

TC1043

DS21347B-page 6

2002 Microchip Technology Inc.

4.0

TYPICAL APPLICATIONS

The TC1043 lends itself to a wide variety of applica-
tions, particularly in battery powered systems. It typi-
cally

finds

application

power

management,

processor supervisory, and interface circuitry.

4.1

Wake-Up Timer

Many microcontrollers have a low power "sleep" mode
that significantly reduces their supply current. Typically,
the microcontroller is placed in this mode via a software
instruction, and returns to a fully enabled state upon
reception of an external signal ("wake-up"). The wake-
up signal is usually supplied by a hardware timer. Most
system applications demand that this timer have a long
duration (typically seconds or minutes), and consume
as little supply current as possible.

The circuit shown in Figure 4-1 is a wake-up timer
made from comparator CMPTR2. (CMPTR2 is used
because the wake-up timer must operate when SHDN
is active.) Capacitor C1 charges through R1 until a volt-
age equal to V

is reached, at which point the WAKE-

UP is driven active. Upon wake-up, the microcontroller
resets the timer by forcing a logic low on a dedicated,
open drain I/O port pin. This discharges C1 through R4
(the value of R4 is chosen to limit the maximum current
sunk by the I/O port pin). With a 3V supply, the circuit
as shown consumes typically 6

A and furnishes a

nominal timer duration of 25 seconds.

4.2

Precision Battery Monitor

Figure 4-2 is a precision battery low/battery dead mon-
itoring circuit. Typically, the battery low output warns
the user that a battery dead condition is imminent. Bat-
tery dead typically initiates a forced shutdown to pre-
vent operation at low internal supply voltages (which
can cause unstable system operation).

The circuit of Figure 4-2 uses a single TC1043 (one op
amp is unused) and only six external resistors. AMP 1
is a simple buffer, while CMPTR1 and CMPTR2 provide
precision voltage detection using V

as a reference.

Resistors R2 and R4 set the detection threshold for
BATTLOW, while resistors R1 and R3 set the detection
threshold for BATTFAIL. The component values shown
assert BATTLOW at 2.2V (typical) and BATTFAIL at
2.0V (typical). Total current consumed by this circuit is
typically 22

A at 3V. Resistors R5 and R6 provide hys-

teresis for comparators CMPTR1

and

CMPTR2

respectively.

4.3

Dual LDO with Shutdown

Figure 4-3 shows a portion of a TC1043 configured as
a dual low dropout regulator with shutdown. AMP1 and
AMP2 are independent error amplifiers that use V

a reference. Resistors RA

, RB

, RA

and RB

set the

feedback around the amplifiers and therefore deter-
mine the output voltage settings (please see equation
in the figure). RA

, RB

, RA

and RB

can have large

ohmic values (i.e. 100's of k

) to minimize supply cur-

rent.

Using the 2N2222 output transistors as shown, these
regulators exhibit low dropout operation. For example,
with V

OUT

= 3.0V, the typical dropout voltage is only

50mV at an output current of 50mA. The unused com-
parators can be used in conjunction with this circuit as
power-on reset or low voltage detectors for a complete
LDO solution at a very low installed cost.

4.4

External Hysteresis

Hysteresis can be set externally with two resistors
using positive feedback techniques (see Figure 4-3).
The design procedure for setting external comparator
hysteresis is as follows:

Choose the feedback resistor R

. Since the

input bias current of the comparator is at most
100pA, the current through R

can be set to

100nA (i.e. 1000 times the input bias current)
and retain excellent accuracy. The current
through R

at the comparator's trip point is V

where V

is a stable reference voltage.

FIGURE 4-1:

WAKE-UP TIMER

Determine the hysteresis voltage (V

) between

the upper and lower thresholds.

Calculate R

as follows:

WAKE-UP

10µF

I/O*

*Open Drain Port Pin

Microcontroller

CMPTR2

TC1043

2002 Microchip Technology Inc.

DS21347B-page 7

TC1043

EQUATION 4-1:

Choose the rising threshold voltage for V

SRC

THR

Calculate R

as follows:

EQUATION 4-2:

Verify the threshold voltages with these formu-
las:

SRC

rising:

EQUATION 4-3:

SRC

falling:

EQUATION 4-4:

4.5

32.768kHz `Time Of Day Clock'
Crystal Controlled Oscillator

A very stable oscillator driver can be designed by using
a crystal resonator as the feedback element. Figure 4-
5 shows a typical application circuit using this tech-
nique to develop a clock driver for a Time-Of-Day
(TOD) clock chip. The value of R

and R

determines

the DC voltage level at which the comparator trips; in
this case one-half of V

. The RC time constant of R

and C

should be set several times greater than the

crystal oscillator's period, which will ensure a 50% duty
cycle by maintaining a DC voltage at the inverting com-
parator input equal to the absolute average of the out-
put signal.

4.6

Non-Retriggerable One Shot Multi-
vibrator

Using two comparators, a non-retriggerable, one shot
multi-vibrator can be designed using the circuit config-
uration of Figure 4-6. A key feature of this design is that
the pulse width is independent of the magnitude of the
supply voltage because the charging voltage and the
intercept voltage are a fixed percentage of V

. In addi-

tion, this one shot is capable of pulse width with as
much as a 99% duty cycle and exhibits input lockout to
ensure that the circuit will not re-trigger before the out-
put pulse has completely timed out. The trigger level is

the voltage required at the input to raise the voltage at
node A higher than the voltage at node B, and is set by
the resistive divider R4 and R10 and the impedance
network composed of R1, R2 and R3. When the one
shot has been triggered, the output of CMPTR2 is high,
causing the reference voltage at the non-inverting input
of CMPTR1 to go to V

. This prevents any additional

input pulses from disturbing the circuit until the output
pulse has timed out.

The value of the timing capacitor C1 must be small
enough to allow CMPTR1 to discharge C1 to a diode
voltage before the feedback signal from CMPTR2
(through R10) switches CMPTR1 to its high state and
allows C1 to start an exponential charge through R5.
Proper circuit action depends upon rapidly discharging
C1 through the voltage set by R6, R9 and D2 to a final
voltage of a small diode drop. Two propagation delays
after the voltage on C1 drops below the level on the
non-inverting input of CMPTR2, the output of CMPTR1
switches to the positive rail and begins to charge C1
through R5. The time delay which sets the output pulse
width results from C1 charging to the reference voltage
set by R6, R9 and D2, plus four comparator propaga-
tion delays. When the voltage across C1 charges
beyond the reference, the output pulse returns to
ground and the input is again ready to accept a trigger
signal.

4.7

Oscillators and Pulse Width
Modulators

Microchip's linear building block comparators adapt
well to oscillator applications for low frequencies (less
than 100kHz). Figure 4-7 shows a symmetrical square
wave generator using a minimum number of compo-
nents. The output is set by the RC time constant of R4
and C1, and the total hysteresis of the loop is set by R1,
R2 and R3. The maximum frequency of the oscillator is
limited only by the large signal propagation delay of the
comparator in addition to any capacitive loading at the
output which degrades the slew rate.

To analyze this circuit, assume that the output is initially
high. For this to occur, the voltage at the inverting input
must be less than the voltage at the non-inverting input.
Therefore, capacitor C1 is discharged. The voltage at
the non-inverting input (V

) is:

EQUATION 4-5:

where, if R1 = R2 = R3, then:

EQUATION 4-6:

-----------

THR

---------------------

-------

-----------------------------------------------------------

TH R

(

)

(

)

-------

THF

THR

D D

(

)

------------------------------

R2 V

(

)

R1 R3

(

)

[

]

---------------------------------------------

2 V

(

)

-------------------

TC1043

DS21347B-page 8

2002 Microchip Technology Inc.

Capacitor C1 will charge up through R4. When the volt-
age at the comparator's inverting input is equal to V

the comparator output will switch. With the output at
ground potential, the value at the non-inverting input
terminal (V

) is reduced by the hysteresis network to a

value given by:

EQUATION 4-7:

Using the same resistors as before, capacitor C1 must
now discharge through R4 toward ground. The output
will return to a high state when the voltage across the
capacitor has discharged to a value equal to V

. The

period of oscillation will be twice the time it takes for the
RC circuit to charge up to one-half its final value. The
period can be calculated from:

EQUATION 4-8:

The frequency stability of this circuit should only be a
function of the external component tolerances.

Figure 4-8 shows the circuit for a pulse width modulator
circuit. It is essentially the same as in Figure 4-7 with
the addition of an input control voltage. When the input
control voltage is equal to one-half V

, operation is

basically the same as described for the free-running
oscillator. If the input control voltage is moved above or
below one-half V

, the duty cycle of the output square

wave will be altered. This is because the addition of the
control voltage at the input has now altered the trip
points. The equations for these trip points are shown in
Figure 4-8 (see V

and V

Pulse width sensitivity to the input voltage variations
can be increased by reducing the value of R6 from
10k

and conversely, sensitivity will be reduced by

increasing the value of R6. The values of R1 and C1
can be varied to produce the desired center frequency.

4.8

Voice Band Receive Filter

The majority of spectral energy for human voices is
found to be in a 2.7kHz frequency band from 300Hz to
3kHz. To properly recover a voice signal in applications
such as radios, cellular phones, and voice pagers, a
low power bandpass filter that is matched to the human
voice spectrum can be implemented using MIcrochip's
CMOS op amps. Figure 4-9 shows a unity gain multi-
pole Butterworth filter with ripple less than 0.15dB in
the human voice band. The lower 3dB cut-off frequency
is 70Hz (single order response), while the upper cut-off
frequency is 3.5kHz (fourth order response).

4.9

Supervisory Audio Tone (SAT)
Filter for Cellular

Supervisory Audio Tones (SAT) provide a reliable
transmission path between cellular subscriber units
and base stations. The SAT tone functions much like
the current/voltage used in land line telephone systems
to indicate that a phone is off the hook. The SAT tone
may be one of three frequencies: 5970, 6000 or
6030Hz. A loss of SAT implies that channel conditions
are impaired and if SAT is interrupted for more than 5
seconds a cellular call is terminated.

Figure 4-10 shows a high Q (30) second order SAT
detection bandpass filter using Microchip's CMOS op
amp architecture. This circuit nulls all frequencies
except the three SAT tones of interest.

-----------

FREQ

-----------------

2 0.694

(

)

(

)

(

)

TC1043

DS21347B-page 10

2002 Microchip Technology Inc.

FIGURE 4-4:

COMPARATOR
EXTERNAL HYSTERESIS
CONFIGURATION

FIGURE 4-5:

32.768 KHZ "TIME-OF-
DAY" CLOCK
OSCILLATOR

FIGURE 4-6:

NON-RETRIGGERABLE MULTI-VIBRATOR

FIGURE 4-7:

SQUARE WAVE GENERATOR

OUT

SRC

TC1043

Comparator

OUT

VDD

150k

100 pF

32.768 kHz

PER

= 30.52 µsec

TC1043

Comparator

CMPTR1

CMPTR2

Out

562k

100k

10M

243k

10M

100 pF

R10
61.9k

GND

TC1025

TC1043

100k

R2 (V

)

R2 + (R1||R3)

) (R2||R3)

R1 + (R2||R3)

FREQ = 1

2(0.694)(R4)(C1)

TC1043

Comparator

2002 Microchip Technology Inc.

DS21347B-page 13

TC1043

5.0

TYPICAL CHARACTERISTICS

Note:

The graphs and tables provided following this note are a statistical summary based on a limited number of
samples and are provided for informational purposes only. The performance characteristics listed herein
are not tested or guaranteed. In some graphs or tables, the data presented may be outside the specified
operating range (e.g., outside specified power supply range) and therefore outside the warranted range.

1.5

2.5

3.5

4.5

5.5

SUPPLY VOLTAGE (V)

Comparator Propagation Delay

vs. Supply Voltage

DELAY TO RISING EDGE (

sec)

Overdrive = 10mV

Overdrive = 50mV

1.5

2.5

3.5

4.5

5.5

DELAY TO FALLING EDGE (

sec)

-40

TEMPERATURE (

°C)

DELAY TO RISING EDGE (

sec)

Overdrive = 100mV

Overdrive = 10mV

Overdrive = 50mV

Comparator Propagation Delay

vs. Supply Voltage

Comparator Propagation Delay

vs. Temperature

= 25°C

= 100pF

= 25°C

= 100pF

Overdrive = 100mV

= 4V

= 5V

= 2V

= 3V

2.5

2.0

1.5

1.0

- V

OUT

(V)

SOURCE

(mA)

-40

Comparator Output Swing
vs. Output Source Current

DELAY TO FALLING EDGE (

sec)

Overdrive = 100mV

2.5

2.0

1.5

1.0

Comparator Propagation Delay

vs. Temperature

Comparator Output Swing

vs. Output Sink Current

TEMPERATURE (

°C)

SINK

(mA)

= 4V

= 5V

= 2V

= 3V

= 25°C

= 3V

= 1.8V

= 5.5V

= 3V

= 1.8V

= 5.5V

OUT

- V

(V)

Sinking

OUTPUT SHORT-CIRCUIT CURRENT (mA)

SUPPLY VOLTAGE (V)

Comparator Output Short-Circuit

Current vs. Supply Voltage

Sourcing

= -40

°C

= -40

°C

= 25

°C

= 85

°C

= 25

°C

= 85

°C

REFERENCE VOLTAGE (V)

1.240

1.220

1.200

1.180

1.160

1.140

LOAD CURRENT (mA)

Reference Voltage vs.

Load Current

= 1.8V

= 3V

= 5.5V

Sinking

Sourcing

= 1.8V

= 3V

= 5.5V

100

200

300

400

SUPPLY AND REFERENCE VOLTAGES (V)

TIME (

µsec)

Line Transient

Response of V

REF

TC1043

DS21347B-page 14

2002 Microchip Technology Inc.

TYPICAL CHARACTERISTICS (CONTINUED)

Op-Amp Short-Circuit Current

vs. Supply Voltage

SUPPLY VOLTAGE (V)

UTPUT CURRENT

(
mA

)

Op-Amp DC Open-Loop Gain

vs. Temperature

TEMPERATURE (

°C)

3000

0.0

1.0

2.0

3.0

4.0

5.0

6.0

2500

2000

1500

1000

500

-40

°C

SINK

SUPPLY VOLTAGE (V)

DC OPEN-LOOP GAIN

(
dB

)

Op-Amp DC Open-Loop Gain

vs. Supply Voltage

140

120

100

0.0

1.0

2.0

3.0

4.0

5.0

6.0

Op-Amp Load Resistance

vs. Load Capacitance

Op-Amp Small-Signal

Transient Response

TIME (

µsec)

(
k

)

UTPUT VOLTAGE

(
mV

)

I
NPUT VOLTAGE

(
mV

)

100

250 500 750 1000

10 20 30 40 50 60 70 80

12501500 1750 2000

100

1000

V
V

= 1.5V

10% Overshoot

Region of Marginal Stability

Region of Stable Operation

Op-Amp Short-Circuit Current

vs. Supply Voltage

SUPPLY VOLTAGE (V)

UTPUT CURRENT

(
mA

)

-5

-10

-15

-20

-25

-30

-35

0.0

1.0

2.0

3.0

4.0

5.0

6.0

SRC

Large-Signal

Transient Response

TIME (

µsec)

10 20 30 40 50 60 70 80

OUTPUT VOLTAGE (mV)

INPUT VOLTAGE (mV)

Op-Amp Power Supply Rejection

Ratio (PSRR) vs. Frequency

FREQUENCY (Hz)

PSRR (dB)

10K

100

-10

-20

-30

-40

-50

-60

-70

100K

= 3V

= 1.5V

IN =

100mV

TC1043

DS21347B-page 16

2002 Microchip Technology Inc.

6.0

PACKAGING INFORMATION

6.1

Package Marking Information

Package marking information not available at this time.

6.2

Taping Information

6.3

Package Dimensions

Component Taping Orientation for 16-Pin QSOP (Narrow) Devices

PIN 1

User Direction of Feed

Standard Reel Component Orientation
for TR Suffix Device

Package

Carrier Width (W)

Pitch (P)

Part Per Full Reel

Reel Size

16-Pin QSOP (N)

12 mm

8 mm

2500

13 in

Carrier Tape, Reel Size, Number of Components Per Reel and Reel Size

MAX.

PIN 1

.157 (3.99)
.150 (3.81)

.196 (4.98)
.189 (4.80)

.011 (0.30)
.007 (0.20)

.010 (0.25)
.004 (0.10)

.069 (1.75)
.053 (1.35)

.010 (0.25)
.007 (0.19)

.050 (1.27)
.015 (0.40)

.244 (6.20)
.227 (5.79)

(0.635)

BSC

16-Pin QSOP (Narrow)

Dimensions: inches (mm)

2002 Microchip Technology Inc.

DS21347B - page 19

TC1043

Information contained in this publication regarding device
applications and the like is intended through suggestion only
and may be superseded by updates. It is your responsibility to
ensure that your application meets with your specifications.
No representation or warranty is given and no liability is
assumed by Microchip Technology Incorporated with respect
to the accuracy or use of such information, or infringement of
patents or other intellectual property rights arising from such
use or otherwise. Use of Microchip's products as critical com-
ponents in life support systems is not authorized except with
express written approval by Microchip. No licenses are con-
veyed, implicitly or otherwise, under any intellectual property
rights.

Trademarks

The Microchip name and logo, the Microchip logo, FilterLab,
K

, microID, MPLAB, PIC, PICmicro, PICMASTER, PIC-

START, PRO MATE, SEEVAL and The Embedded Control Solu-
tions

Company

are

registered

trademarks

Microchip

Technology Incorporated in the U.S.A. and other countries.

dsPIC, ECONOMONITOR, FanSense, FlexROM, fuzzyLAB,
In-Circuit Serial Programming, ICSP, ICEPIC, microPort,
Migratable Memory, MPASM, MPLIB, MPLINK, MPSIM,
MXDEV, PICC, PICDEM, PICDEM.net, rfPIC, Select Mode
and Total Endurance are trademarks of Microchip Technology
Incorporated in the U.S.A.

Serialized Quick Turn Programming (SQTP) is a service mark
of Microchip Technology Incorporated in the U.S.A.

All other trademarks mentioned herein are property of their
respective companies.

Printed on recycled paper.

Microchip received QS-9000 quality system
certification for its worldwide headquarters,
design and wafer fabrication facilities in
Chandler and Tempe, Arizona in July 1999
and Mountain View, California in March 2002.
The Company's quality system processes and
procedures are QS-9000 compliant for its
PICmicro

8-bit MCUs, K

code hopping

devices, Serial EEPROMs, microperipherals,
non-volatile memory and analog products. In
addition, Microchip's quality system for the
design and manufacture of development
systems is ISO 9001 certified.

DS21347B-page 30

2002 Microchip Technology Inc.

AMERICAS

Corporate Office

2355 West Chandler Blvd.
Chandler, AZ 85224-6199
Tel: 480-792-7200 Fax: 480-792-7277
Technical Support: 480-792-7627
Web Address: http://www.microchip.com

Rocky Mountain

2355 West Chandler Blvd.
Chandler, AZ 85224-6199
Tel: 480-792-7966 Fax: 480-792-7456

Atlanta

500 Sugar Mill Road, Suite 200B
Atlanta, GA 30350
Tel: 770-640-0034 Fax: 770-640-0307

Boston

2 Lan Drive, Suite 120
Westford, MA 01886
Tel: 978-692-3848 Fax: 978-692-3821

Chicago

333 Pierce Road, Suite 180
Itasca, IL 60143
Tel: 630-285-0071 Fax: 630-285-0075

Dallas

4570 Westgrove Drive, Suite 160
Addison, TX 75001
Tel: 972-818-7423 Fax: 972-818-2924

Detroit

Tri-Atria Office Building
32255 Northwestern Highway, Suite 190
Farmington Hills, MI 48334
Tel: 248-538-2250 Fax: 248-538-2260

Kokomo

2767 S. Albright Road
Kokomo, Indiana 46902
Tel: 765-864-8360 Fax: 765-864-8387

Los Angeles

18201 Von Karman, Suite 1090
Irvine, CA 92612
Tel: 949-263-1888 Fax: 949-263-1338

New York

150 Motor Parkway, Suite 202
Hauppauge, NY 11788
Tel: 631-273-5305 Fax: 631-273-5335

San Jose

Microchip Technology Inc.
2107 North First Street, Suite 590
San Jose, CA 95131
Tel: 408-436-7950 Fax: 408-436-7955

Toronto

6285 Northam Drive, Suite 108
Mississauga, Ontario L4V 1X5, Canada
Tel: 905-673-0699 Fax: 905-673-6509

ASIA/PACIFIC

Australia

Microchip Technology Australia Pty Ltd
Suite 22, 41 Rawson Street
Epping 2121, NSW
Australia
Tel: 61-2-9868-6733 Fax: 61-2-9868-6755

China - Beijing

Microchip Technology Consulting (Shanghai)
Co., Ltd., Beijing Liaison Office
Unit 915
Bei Hai Wan Tai Bldg.
No. 6 Chaoyangmen Beidajie
Beijing, 100027, No. China
Tel: 86-10-85282100 Fax: 86-10-85282104

China - Chengdu

Microchip Technology Consulting (Shanghai)
Co., Ltd., Chengdu Liaison Office
Rm. 2401, 24th Floor,
Ming Xing Financial Tower
No. 88 TIDU Street
Chengdu 610016, China
Tel: 86-28-6766200 Fax: 86-28-6766599

China - Fuzhou

Microchip Technology Consulting (Shanghai)
Co., Ltd., Fuzhou Liaison Office
Unit 28F, World Trade Plaza
No. 71 Wusi Road
Fuzhou 350001, China
Tel: 86-591-7503506 Fax: 86-591-7503521

China - Shanghai

Microchip Technology Consulting (Shanghai)
Co., Ltd.
Room 701, Bldg. B
Far East International Plaza
No. 317 Xian Xia Road
Shanghai, 200051
Tel: 86-21-6275-5700 Fax: 86-21-6275-5060

China - Shenzhen

Microchip Technology Consulting (Shanghai)
Co., Ltd., Shenzhen Liaison Office
Rm. 1315, 13/F, Shenzhen Kerry Centre,
Renminnan Lu
Shenzhen 518001, China
Tel: 86-755-2350361 Fax: 86-755-2366086

Hong Kong

Microchip Technology Hongkong Ltd.
Unit 901-6, Tower 2, Metroplaza
223 Hing Fong Road
Kwai Fong, N.T., Hong Kong
Tel: 852-2401-1200 Fax: 852-2401-3431

India

Microchip Technology Inc.
India Liaison Office
Divyasree Chambers
1 Floor, Wing A (A3/A4)
No. 11, O'Shaugnessey Road
Bangalore, 560 025, India
Tel: 91-80-2290061 Fax: 91-80-2290062

Japan

Microchip Technology Japan K.K.
Benex S-1 6F
3-18-20, Shinyokohama
Kohoku-Ku, Yokohama-shi
Kanagawa, 222-0033, Japan
Tel: 81-45-471- 6166 Fax: 81-45-471-6122

Korea

Microchip Technology Korea
168-1, Youngbo Bldg. 3 Floor
Samsung-Dong, Kangnam-Ku
Seoul, Korea 135-882
Tel: 82-2-554-7200 Fax: 82-2-558-5934

Singapore

Microchip Technology Singapore Pte Ltd.
200 Middle Road
#07-02 Prime Centre
Singapore, 188980
Tel: 65-6334-8870 Fax: 65-6334-8850

Taiwan

Microchip Technology Taiwan
11F-3, No. 207
Tung Hua North Road
Taipei, 105, Taiwan
Tel: 886-2-2717-7175 Fax: 886-2-2545-0139

EUROPE

Denmark

Microchip Technology Nordic ApS
Regus Business Centre
Lautrup hoj 1-3
Ballerup DK-2750 Denmark
Tel: 45 4420 9895 Fax: 45 4420 9910

France

Microchip Technology SARL
Parc d'Activite du Moulin de Massy
43 Rue du Saule Trapu
Batiment A - ler Etage
91300 Massy, France
Tel: 33-1-69-53-63-20 Fax: 33-1-69-30-90-79

Germany

Microchip Technology GmbH
Gustav-Heinemann Ring 125
D-81739 Munich, Germany
Tel: 49-89-627-144 0 Fax: 49-89-627-144-44

Italy

Microchip Technology SRL
Centro Direzionale Colleoni
Palazzo Taurus 1 V. Le Colleoni 1
20041 Agrate Brianza
Milan, Italy
Tel: 39-039-65791-1 Fax: 39-039-6899883

United Kingdom

Arizona Microchip Technology Ltd.
505 Eskdale Road
Winnersh Triangle
Wokingham
Berkshire, England RG41 5TU
Tel: 44 118 921 5869 Fax: 44-118 921-5820

03/01/02

ORLDWIDE

ALES

AND

ERVICE

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