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Product Description

Ordering Information

Typical Applications

Features

Functional Block Diagram

RF Micro Devices, Inc.
7628 Thorndike Road
Greensboro, NC 27409, USA

Tel (336) 664 1233

Fax (336) 664 0454

http://www.rfmd.com

Optimum Technology Matching® Applied

Si BJT

GaAs MESFET

GaAs HBT

Si Bi-CMOS

SiGe HBT

Si CMOS

InGaP/HBT

GaN HEMT

SiGe Bi-CMOS

Prescaler

128/129 or

64/65

Phase

Detector &

Charge Pump

RES

TR+

LOOP F

L
T

OSC SEL

RES

TR-

TX OUT

Gain

Control

Ref.

Select

OSC B1

OSC E

OSC B2

VRE

PRESCL OUT

MOD CTRL

DIV CTRL

L AD

VCO TU

RF2513

UHF TRANSMITTER

· Single- or Dual-Channel LO Source
· FM/FSK Transmitter
· Wireless Data Transmitters

· 433/868/915MHz ISM Band Systems
· Wireless Security Systems

The RF2513 is a monolithic integrated circuit intended for
use as a low-cost frequency synthesizer and transmitter.
The device is provided in a 24 pin SSOP package and is
designed to provide a phased locked frequency source
for use in local oscillator or transmitter applications. The
chip can be used in FM or FSK applications in the U.S.
915MHz ISM band and European 433MHz or 868MHz
ISM band. The integrated VCO, dual-modulus/dual-divide
(128/129 or 64/65) prescaler, and reference oscillator
require only the addition of an external crystal to provide
a complete phase-locked oscillator. A second reference
oscillator is available to support two channel applications.

· Fully Integrated PLL Circuit
· 10mW Output Power at 433MHz
· 2.7V to 5.0V Supply Voltage
· Low Current and Power Down Capability
· 300MHz to 1000MHz Frequency Range
· Narrowband and Wideband FM

RF2513

UHF Transmitter

RF2513 PCBA-L Fully Assembled Evaluation Board, 433MHz
RF2513 PCBA-M Fully Assembled Evaluation Board, 868MHz
RF2513 PCBA-H Fully Assembled Evaluation Board, 915MHz

Rev B12 021008

8°MAX

0°MIN

0.050
0.016

0.0098
0.0075

0.2440
0.2284

0.025

0.012
0.008

0.0688
0.0532

0.157
0.150

0.0098
0.0040

0.344
0.337

Package Style: SSOP-24

NOT FOR NEW DESIGNS

See Upgraded Product

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Absolute Maximum Ratings

Parameter

Rating

Unit

Supply Voltage

-0.5 to +5.5

Power Down Voltage (V

)

-0.5 to V

Operating Ambient Temperature

-40 to +85

°C

Storage Temperature

-40 to +150

°C

Parameter

Specification

Unit

Condition

Min.

Typ.

Max.

Overall

T=25 °C, V

=3.6V, Freq=915MHz

Frequency Range

300 to 1000

MHz

Modulation

FM/FSK

Modulation Frequency

MHz

Maximum FM Deviation

200

kHz

Dependent upon Supply Voltage

PLL and Prescaler

Prescaler Divide Ratio

64/65 or 128/129

PLL Lock TIme

4/PLL BW

The PLL lock time, from power up, is set

externally by the bandwidth of the loop filter.

PLL Phase Noise

-72

dBc/Hz

10kHz Offset, 10kHz loop bandwidth

-95

dBc/Hz

100kHz Offset, 10kHz loop bandwidth

Reference Frequency

MHz

Max Crystal R

100

Charge Pump Current

-40

+40

Transmit Section

Maximum Power Level

dBm

Freq=433MHz

-1

dBm

Freq=915MHz

Power Control Range

Power Control Sensitivity

dB/V

Antenna Port Impedance

TX ENABL="1"

Antenna Port VSWR

1.5:1

TX Mode

Modulation Input Impedance

Harmonics

-23

dBc

Spurious

dBc

Compliant to Part 15.249 and I-ETS 300 220

Power Down Control

Logic Controls "ON"

2.0

Voltage supplied to the input; device is "ON"

Logic Controls "OFF"

1.0

Voltage supplied to the input; device is "OFF"

Control Input Impedance

Turn On Time

5 + 4/PLL

From Change in OSC SEL,7.075MHz XTAL

Turn Off Time

From Change in OSC SEL,7.075MHz XTAL

Power Supply

Voltage

3.6

Specifications

2.7 to 5.0

Operating limits

Current Consumption

TX Mode, LVL ADJ=3.6V

TX Mode, LVL ADJ=0V

PLL Only

LVL ADJ=0V, PLL ENABL=0V,

TX ENABL=0V, OSC SEL=0V

Caution! ESD sensitive device.

RF Micro Devices believes the furnished information is correct and accurate
at the time of this printing. However, RF Micro Devices reserves the right to
make changes to its products without notice. RF Micro Devices does not
assume responsibility for the use of the described product(s).

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Pin

Function

Description

Interface Schematic

OSC B2

This pin is connected directly to the reference oscillator transistor base.

The intended reference oscillator configuration is a modified Colpitts.

An appropriate capacitor as chosen by the customer should be con-

nected between pin 1 and pin 2.

OSC E

This pin is connected directly to the emitter of the reference oscillator

transistor. An appropriate capacitor as chosen by the customer should

be connected from this pin to ground.

See pin 1.

OSC B1

This pin is connected directly to the reference oscillator transistor base.

The intended reference oscillator configuration is a modified Colpitts.

An appropriate capacitor as chosen by the customer should be con-

nected between pin 3 and pin 2.

See pin 1.

PLL ENABL

This pin is used to power up or down the VCO and PLL. A logic high

(PLL ENABL>2.0V) powers up the VCO and PLL electronics. A logic

low (PLL ENABL<1.0V) powers down the PLL and VCO.

GND1

Ground connection for the PA buffer amp. Keep traces physically short

and connect immediately to ground plane for best performance.

VCC3

This pin is used to supply DC bias to the transmitter PA. A RF bypass

capacitor should be connected directly to this pin and returned to

ground. A 100pF capacitor is recommended for 915MHz applications.

A 220pF capacitor is recommended for 433MHz applications.

LVL ADJ

This pin is used to vary the transmitter output power. An output level

adjustment range greater than 12dB is provided through analog volt-

age control of this pin. DC current of the transmitter power amp ia also

reduced with output power. This pin MUST be low when the transmitter

is disabled.

TX OUT

RF output pin for the transmitter electronics. TX OUT output impedance

is a low impedance when the transmitter is enabled. TX OUT is a high

impedance when the transmitter is disabled.

GND2

Ground connection for the Tx PA functions. Keep traces physically

short and connect immediately to ground plane for best performance.

VCC1

This pin is used to supply DC bias to the PA buffer amp. A RF bypass

capacitor should be connected directly to this pin and returned to

ground. A 100pF capacitor is recommended for 915MHz applications.

A 220pF capacitor is recommended for 433MHz applications.

TX ENABL

Enables the transmitter circuits. TX ENABL>2.0V powers up all trans-

mitter functions. TX ENABL<1.0V turns off all transmitter functions

except the PLL functions.

PRESCL

OUT

Dual-modulus/Dual-divide prescaler output. The output can be inter-

faced to an external PLL IC for additional flexibility in frequency pro-

gramming.

VREF P

Bias voltage reference pin for bypassing the prescaler and phase

detector. The bypass capacitor should be of appropriate size to provide

filtering of the reference crystal frequency and be connected directly to

this pin.

OSC E

OSC B1

OSC B2

50 k

PLL ENABL

400

4 k

LVL ADJ

40 k

TX OUT

40 k

20 k

TX ENABL

PRESCL
OUT

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Pin

Function

Description

Interface Schematic

MOD CTRL

This pin is used to select the prescaler modulus. A logic "high" selects

64 or 128 for the prescaler divisor. A logic "low" selects 65 or 129 for

the prescaler divisor.

DIV CTRL

This pin is used to select the desired prescaler divisor. A logic "high"

selects the 64/65 divisor. A logic low selects the 128/129 divisor.

MOD IN

FM analog or digital modulation can be imparted to the VCO through

this pin. The VCO varies in accordance to the voltage level presented

to this pin. To set the deviation to a desired level, a voltage divider refer-

enced to Vcc is the recommended. Because the modulation varactors

are part of the resonator tank, the deviation is slightly dependent upon

the components used in the external tank.

See pin 18.

VCC2

This pin is used to is supply DC bias to the VCO, prescaler, and PLL.

RESNTR-

The RESNTR pins are used to supply DC voltage to the VCO, as well

as to tune the center frequency of the VCO. Equal value inductors

should be connected to this pin and pin 20.

Not internally connected.

RESNTR+

See pin 18.

GND3

GND is the ground shared on chip by the VCO, prescaler, and PLL

electronics. Keep traces physically short and connect immediately to

ground plane for best performance.

VCO TUNE

Loop filter input to VCO.

LOOP FLT

OUT

Output of the charge pump. An RC network from this pin to ground is

used to establish the PLL bandwidth.

OSC SEL

A logic high (OSC SEL>2.0V) applied to this pin powers on reference

oscillator 2 and powers down reference oscillator 1. A logic low (OSC

SEL<1.0V) applied to this pin powers on reference oscillator 1 and

powers down reference oscillator 2.

ESD

This diode structure is used to provide electrostatic discharge protec-

tion to 3kV using the Human body model. The following pins are pro-

tected: 1-3, 9, 10,12-15, 17, 21-23.

MOD CTL

DIV CTL

RESNTR-

RESNTR+

4 k

MOD IN

RESNTR-

RESNTR+

4 k

VCO TUN

LOOP FLT

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RF2513 Theory of Operation

Introduction
The RF2513 is a low-cost FM/FSK UHF transmitter
designed for applications operating within the 300MHz
to 1000MHz frequency range. It is particularly intended
for 315/433/868MHz band systems, remote keyless
entry systems, and FCC Part 15.231 periodic transmit-
ters. It can also be used as a single- or dual-channel
local oscillator signal source. The integrated VCO,
phase detector, prescaler, and reference oscillator
require only the addition of an external crystal to pro-
vide a complete phase-locked loop.

The RF2513 is provided in a 24-pin SSOP-24 package
and is designed to operate from a supply voltage rang-
ing from 2.7V to 5.0V, accommodating designs using
three NiCd battery cells, two AAA flashlight cells, or a
lithium button battery. The device is capable of provid-
ing up to 10mW output power into a 50

load

(+10dBm) and is intended to comply with FCC require-
ments for unlicensed remote control transmitters.

RF2513 Functional Blocks
A PLL consists of a reference oscillator, phase detec-
tor, loop filter, voltage controlled oscillator (VCO), and
a programmable divider in the feedback path. The
RF2513 includes all of these internally, except for the
loop filter and the reference oscillator's crystal and two
feedback capacitors.

The

reference oscillators are Colpitts type oscillators.

Pins 1 (OSC B2), 2 (OSC E), and 3 (OSC B1) provide
connections to the internal transistors used as refer-
ence oscillators. The Colpitts configuration is a low
parts-count topology with reliable performance and
reasonable phase noise. Alternatively, an external sig-
nal could be injected into the base of either transistor.
In either case, the drive level should be around
500mV

. This level prevents overdriving the device

and keeps phase noise and reference spurs minimal.

The user sets which oscillator is operational by setting
pin 24 (OSC SEL) either high or low. This allows the
implementation of two channel systems.

The

prescaler divides the Voltage Controlled Oscilla-

tor (VCO) frequency down by either 64/65 or 128/129,
using a series of flip-flops, depending upon the logic
level present at pin 15 (DIV CTRL). A high logic level
will select the 64/65 divisor. A low logic level will select
the 128/129 divisor. This divided signal is then fed into
the phase detector where it is compared with the refer-
ence frequency.

In addition to the DIV CTRL setting, one also sets the
prescaler modulus by setting pin 14 (MOD CTRL)
either high or low. A high logic level will select the
64/128 divisor. A low logic level will select the 65/129
divisor.

Pin 12 (PRESCL OUT) provides access to the pres-
caler output. This is used for interfacing to an external
PLL IC.

The RF2513 contains an onboard phase detector and
charge pump. The

phase detector compares the

phase of the reference oscillator to the phase of the
VCO. The phase detector is implemented using flip-
flops in a topology referred to as either "digital
phase/frequency detector" or "digital tri-state compara-
tor". The circuit consists of two D flip-flops whose out-
puts are combined with a NAND gate which is then tied
to the reset on each flip-flop. The outputs of the flip-
flops are also connected to the charge pump. Each flip-
flop output signal is a series of pulses whose fre-
quency is related to the flip-flop input frequency.

When both inputs of the flip-flops are identical, the sig-
nals are both frequency and phase locked. If they are
different, they will provide signals to the charge pump
which will either charge or discharge the loop filter or
enter into a high impedance state. This is where the
name "tri-state comparator" comes from.

The main benefit of this type of detector it's ability to
correct for errors in both phase and frequency. When
locked, the detector uses phase error for correction.
When unlocked, it will use the frequency error for cor-
rection. This type of detector will lock under all condi-
tions.

The prescaler and the phase detector bias voltage is
brought out through pin 13 (VREF P). This allows
bypassing of the of these two circuits to filter the refer-
ence crystal frequency.

The

charge pump consists of two transistors, one for

charging the loop filter and the other for discharging
the loop filter. It's inputs are the outputs of the phase
detector flip-flops. Since there are two flip-flops, there
are four possible states. If both amplifier inputs are low,
then the amplifier pair goes into a high impedance
state, maintaining the charge on the loop filter. The
state where both inputs are high will not occur. The
other states are either charging or discharging the loop
filter. The loop filter integrates the pulses coming from

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the charge pump to create a control voltage for the
voltage controlled oscillator.

The

voltage controlled oscillator (VCO) is a tuned

differential amplifier with the bases and collectors
cross-coupled to provide positive feedback and a 360°
phase shift. The tuned circuit is located in the collec-
tors. It is comprised of internal varactors and two exter-
nal inductors. The designer selects the inductors for
the desired frequency of operation. These inductors
also provide DC bias for the VCO. The output of the
VCO is buffered and applied to the prescaler circuit,
where it is divided down and compared to the refer-
ence oscillator frequency.

The PLL and VCO circuitry can be enabled by setting
applying a "high" logic level to pin 4 (PLL ENABL).
Conversely, the PLL and VCO circuitry will be turned
off if the level is tied "low".

The

transmit amplifier is a two stage amplifier con-

sisting of a driver and an open collector final stage. It is
capable of providing 8dBm of output power into a 50

load while operating from a 3.6V power supply.

The output power is adjustable by the setting of pin 7
(LVL ADJ). This analog input allows the designer a
15dB range of output power. As the LVL ADJ voltage is
reduced, the output power and current consumption
are reduced. LVL ADJ must be low when the transmit-
ter is disabled.

Additionally, the transmitter circuitry can be disabled
entirely by applying a "low" logic level to pin 11 (TX
ENABL). During transmission, this pin should be tied
"high". This pin controls all circuitry except for the PLL
circuitry.

During transmission the transmitter is enabled and the
impedance of the output pin, pin 8 (TX OUT), is low.
When the transmitter is not enabled, the impedance
becomes high.

The RF2513 contains onboard band gap reference
voltage circuitry which provides a stable

DC bias over

varying temperature and supply voltages.

Designing with the RF2513
The

reference oscillator is built around the onboard

transistor at pins 1, 2 and 3. The intended topology is
of a Colpitts oscillator. The Colpitts oscillator is quite
common and requires few external components, mak-
ing it ideal for low cost solutions. The topology of this
type of oscillator is as seen in the following figure.

This type of oscillator is a parallel resonant circuit for a
fundamental mode crystal. The transistor amplifier is
an emitter follower and the voltage gain is developed
by the tapped capacitor impedance transformer. The
series combination of C

and C

act in parallel with the

input capacitance of the transistor to capacitively load
the crystal.

The nominal capacitor values can be calculated with
the following equations.

and

The load capacitance is usually 32pF. The variable freq
is the oscillator frequency in MHz. The frequency can
be adjusted by either changing C

or by placing a vari-

able capacitor in series with the crystal. As an exam-
ple, assume a desired frequency of 14MHz and a load
capacitance of 32pF. C

=137.1pF and C

=41.7pF.

These capacitor values provide a starting point. The
drive level of the oscillator should be checked by look-
ing at the signal at pin 2 (OSC E). It has been found
that the level at this pin should generally be around
500mV

or less. This will reduce the reference spur

levels and reduce noise from distortion. If this level is
higher than 500mV

then decrease the value of C

The values of these capacitors are usually tweaked
during design to meet performance goals, such as
minimizing the start-up time.

Additionally, by placing a variable capacitor in series
with the crystal, one is able to adjust the frequency.
This will also alter the drive level, so it should be
checked again.

An important part of the overall design is the voltage
controlled oscillator (VCO). The VCO is configured as
a differential amplifier. The VCO is tuned via the exter-
nal inductors, capacitor and varactor. The varactor
capacitance is set by the loop filter output voltage
through a 4k

resistor.

60 C

load

freq

MHz

------------------------

load

-------------

------

--------------------------

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To tune the VCO the designer only needs to calculate
the value of the inductors connected to pins 18 and 20
(RESNTR- and RESNTR+). The inductor value is
determined by the following equation.

In this equation, f is the desired operating frequency
and L is the value of the inductor required. The value C
is the amount of capacitance presented by the varac-
tor, capacitor and parasitics. The factor of one half is
due to the inductors being in each leg.

The setup of the VCO can be summarized as follows.
First, open the loop. Next, get the VCO to run on the
desired frequency by selecting the proper inductor and
capacitor values. The capacitor value will need to
include the varactor and circuit parasitics. After the
VCO is running at the desired frequency, then set the
VCO sensitivity.

The sensitivity is determined by connecting the control
voltage input point to ground and noting the frequency.
Then connect the same point to the supply and again
note the frequency. The difference between these two
frequencies divided by the supply voltage is the VCO
sensitivity expressed in Hz/V. Increasing the inductor
value while decreasing the capacitor value will
increase the sensitivity. Decreasing the inductor value
while increasing the capacitor value will lower the sen-
sitivity.

When increasing or decreasing component values,
make sure that the center frequency remains constant.
Finally, close the loop.

External to the part, the designer needs to implement a
loop filter to complete the PLL. The loop filter converts
the output of the charge pump into a voltage that is
used to control the VCO. Internally, the VCO is con-

nected to the charge pump output through an internal
4k

resistor. The loop filter is then connected in paral-

lel to this point at pin 23 (LOOP FLT). This limits the
loop filter topology to a second order filter usually con-
sisting of a shunt capacitor and a shunt series RC. A
passive filter is most common, as it is a low cost and
low noise design. An additional pole could be used for
reducing the reference spurs, however there is not a
way to add the series resistor. This should not be a
reason for concern however.

The schematic of the loop filter is as follows.

The transfer function is

where the time constants are defined as

and

The frequency at which unity gain occurs is given by

This is also the loop bandwidth.

If the phase margin (PM) and the loop bandwidth
(

LBW

) are known, it is possible to calculate the time

constants. These are found using the following equa-
tions.

and

With these known, it is then possible to determine the
values of the filter components.

RESNTR-

RESNTR+

LOOP

FLT

4 k

----------------

---- 1

---

VCO

Loop Filter

Charge Pump

F s

( )

(

)

------------------------------------------

-------------------

LBW

-------------------

(

)

sec

(

)

tan

LBW

--------------------------------------------------

LBW

--------------------------

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As an example, consider a loop bandwidth of 50kHz, a
phase margin of 45°, a divide ratio of 64, a K

VCO

20MHz/V, and a K

of 40

A/2

rad. Time constant

is 1.31848

s, time constant

is 7.68468

s, C

8.35pF, C

is 40.3pF, and R

is 190.6k

In order to perform these calculations, one will need to
know the value of two constants, K

VCO

and K

. K

calculated by dividing the charge pump current by 2

For the RF2513, the charge pump current is 40

VCO

is best found empirically as it will change with

frequency and board parasitics. By briefly connecting
pin 23 (LOOP FLT) to VCC and then to ground, the fre-
quency tuning range of the VCO can be seen. Dividing
the difference between these two frequencies by the
difference in the voltage gives K

VCO

in MHz/V.

The control lines provide an

interface for connecting

the device to a microcontroller or other signal generat-
ing mechanism. The designer can treat pin 16 (MOD
IN), pin 15 (DIV CTRL), pin 14 (MOD CTRL), pin 24
(OSC SEL), and pin 7 (LVL ADJ) as control pins whose
voltage level can be set.

General

RF bypassing techniques must be observed

to get the best performance. Choose capacitors such
that they are series resonant near the frequency of
operation.

Board layout is always an area in which great care
must be taken. The board material and thickness are
used in calculating the RF line widths. The use of vias
for connection to the ground plane allows one to con-
nect to ground as close as possible to ground pins.
When laying out the traces around the VCO, it is desir-
able to keep the parasitics equal between the two legs.
This will allow equal valued inductors to be used.

Pre-compliance testing should be performed during
the design process. This can be done with a GTEM cell
or at a compliance testing laboratory. It is recom-

mended that pre-compliance testing be performed so
that there are no surprises during final compliance
testing. This will help keep the product development
and release on schedule.

Working with a laboratory offers the benefit of years of
compliance testing experience and familiarity with the
regulatory issues. Also, the laboratory can often pro-
vide feedback that will help the designer make the
product compliant.

On the other hand, having a GTEM cell or an open air
test site locally offers the designer the ability to rapidly
determine whether or not design changes impact the
product's compliance. Set-up of an open air test site
and the associated calibration is not trivial. An alterna-
tive is to use a GTEM test cell.

After the design has been completed and passes com-
pliance testing, application will need to be made with
the respective regulatory bodies for the geographic
region in which the product will be operated to obtain
final certifications.

Conclusions
The RF2513 is an FM/FSK UHF transmitter that fea-
tures a phase-locked output. This device is suitable for
use in a CFR Part 15.231 compliant product as well as
a local oscillator signal source. Two examples of show-
ing these applications have been provided. Further, the
RF2513 is packaged in a low cost SSOP-24 plastic
package and requires few external parts, thus making
it suitable for low cost designs.

-----

VCO

LBW

-----------------------------

LBW

(

)

LBW

(

)

----------------------------------------

----- 1

------

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Evaluation Board Schematic

H (915MHz) and M (868MHz) Boards

(Download Bill of Materials from www.rfmd.com.)

Phase

Detector/

Charge Pump

Prescaler

Ref

Select

Gain

Control

PLL ON

100 pF

4 pF

8.2 nH

4 pF

C18

100 nF

strip

RF OUT

VCC

LVL ADJ

10 nF

22 pF

VCC

10 nF

C10

22 pF

TX EN

R2*

PRESC OUT

6.8 nH

56 nH

C12

10 nF

C13

22 pF

C14

4.7

C16

C17

OSC SEL

MOD CTL

DIV 64

strip

MOD IN

C11

0.1

2513401A, 402A

M (868MHz)

H (915MHz)

Board

13.57734

7.15909

X1 (MHz)

13.41015

7.07549

X2 (MHz)

8.2

6.8

L2 (nH)

2.2

5.1

R1 (k

)

47 nF

22 nF

C16 (nF)

4.7

2.2

C17 (nF)

100 pF

C2*

100 pF

X2*

R3*
0

R4*
0

C20

3-10 pF

D1*

D2*

R5*
0

AUDIO

P2-3

TX EN

GND

P2-1

PRESC OUT

P1-1

LVL ADJ

GND

P1-3

PLL ON

P3-5

VCC

GND

P3-3

OSCSLT

GND

P3-1

AUDIO

P4-3

MOD CTL

GND

P4-1

DIV 64

* Denotes optional. These parts are not normally populated.

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Evaluation Board Schematic

L (433MHz) Board

Phase

Detector/

Charge Pump

Prescaler

Ref

Select

Gain

Control

PLL ON

100 pF

8 pF

22 nH

15 pF

C18

100 nF

strip

RF OUT

VCC

LVL ADJ

10 nF

100 pF

VCC

10 nF

C10

100 pF

TX EN

R2*

PRESC OUT

39 nH

220 nH

C12

10 nF

C13

100 pF

C14

4.7

C16

22 nF

C17

2.2 nF

4.7 k

OSC SEL

MOD CTL

DIV 64

strip

MOD IN

C11

0.1

2513400A

22 nH

C19

8 pF

100 pF

C2*

100 pF

6.78 MHz

X2*

R3*
0

R4*
0

C21

3-10 pF

D1*

D2*

R5*
0

AUDIO

P3-1

AUDIO

GND

P3-5

VCC

P3-3

OSCSLT

P4-1

DIV 64

GND

P4-3

MOD CTL

P2-1

PRESC OUT

P2-3

TX EN

GND

P1-1

LVL ADJ

GND

P1-3

PLL ON

Ð­Ð»ÐµÐºÑ‚Ñ€Ð¾Ð½Ð½Ñ‹Ð¹ ÐºÐ¾Ð¼Ð¿Ð¾Ð½ÐµÐ½Ñ‚: RF2513PCBA-L

ÐÐ»ÐµÐºÑ‚Ñ€Ð¾Ð½Ð½Ñ‹Ð¹ ÐºÐ¾Ð¼Ð¿Ð¾Ð½ÐµÐ½Ñ‚: RF2513PCBA-L